منو کاربری

PLL SAA1057 / PIC16F84 from 500kHz to 30MHz

Picture : Our PLL, look the mouse for wired remote control.

This circuit is described in the site www.freddospage.nl, where software can be downloaded.

Although PLL SAA1057 to be discontinued, is possible finds it at low prices in the Brazilian market (R$3,50 = US$1,50).

We made the assembly in UGLY method, with small modifications.

Original project (we add 3 capacitors of 100nF):

The sigle modification was the addition of three capacitors of 100nF. This modification was necessary therefore we use a three buttons PC mouse for the place of the switches STEP, UP and DOWN, thus the control was by hand. E due to the length of the mouse cable was necessary to decoupling the RF.

The power supply comes from the Oscillator to be controlled.

Picture : We use flat cable from computer scrap, it does ease the building.

The signal of RF for frequency control, the tension of frequency control for varicaps as well as the power supply had been connected by a single DIN plug. Later we normalize our interconnections with a mini estereo banana (P2) and are necessary two, one for VCC and incoming RF signal another for referency tension for varicap.

Picture: 2nd PLL built, we use standard cupper board and the LCD is direct connected.

Picture: 2nd PLL, showing the board LCD connections.

The greater inconvenient of this PLL there is no offset, it shows the controlled frequency in kHz. Another problem is the 1kHz step size that it does not allow a fine adjustment in CW or digital modes.

The easiness of assembly, the low cost and the performance are excellent.

Picture: Oscillator 11 to 11.5MHz using a ceramic resonator PLL controlled, it works fine dispite the small size. It is used with BITX15 and ARARINHA 21MHz wich has 10MHz IF. The new oscillators have connections with PLL by two banana stereo plug, it is ease to make small size holes in the case box.

73 from py2ohh miguel

22Bahman

وات متر و برگشت سنج جديد

دوست عزيزم اقاي محمد رضا رنجكش اين دستگاه را ساخته اند

recever radio

Many thanks to David Ai2A for the excellent revision of the following text

40 m Band Superhet Receiver

By the addition of one integrated circuit and some passive components, I was able to convert my earlier developed 40-meter direct conversion receiver design into a superhet model. Anyone who has listened to 40 meters during the evening hours on the crowded 40 m band will appreciate the advantages of the single signal reception, which this circuit offers. All simple direct conversion receiver designs suffer from degraded selectivity performance and are more subject to overload by contrasted to even modest superhet designs. Direct conversion designs are simpler by contrast because they are missing an IF stage and any associated filtering, a BFO and the second mixer.

In order to modify the design to create a superhet model, it was necessary to increase the 1st oscillator frequency from 7000 kHz - 7040 kHz to a revised range of 10686 kHz -10731 kHz (operating frequency plus the intermediate frequency). The choice of this 1st oscillator frequency turned out to be fairly easy by considering the availability of 3686 kHz crystals. Bandwidth is set to 200 Hz by a series coupled filter (using a single 3686 kHz crystal) in the IF amplifier section. This choice is highly suitable for CW operation. The choice of 3686 kHz IF allows use of readily available 10.7 mHz ceramic resonator in the 1st oscillator circuit.

Fig.1: Receiver circuit diagram

The first part of the circuit to be described is the 1st oscillator (main tuning). It is a variation of the Colpitts type oscillator. It uses a 10,7 ceramic resonator as its frequency-determining component. Unlike a quartz crystal based VXO, the ceramic resonator Q1 results in a much broader tuning range (approximately 45 kHz) while still maintaining a desired level of frequency stability at the same time.

A second ceramic resonator with a center frequency of 7020 kHz is used as a front-end filter. This effectively attenuates much of the strong S9 +40 dB strong signal interference from the 41-meter shortwave broadcast band. The shape factor and center frequency, while not a perfect choice, perform quite well. The stop band for this resonator appears to be located at 7125 kHz - well beyond the desired 7040 kHz. The availability, low price, simplicity of the circuit and absence of alignment warrant suggest inclusion of this specific device. A network formed by L1 and L2 help match the 330 ohms resonator impedance to the 50 ohms of the diode ring mixer and the antenna.

The output of the ring diode mixer is coupled to an IF stage based on the NE592 broadband amplifier. I was able to narrow the IF selectivity to 200 Hz by adding a crystal filter using series interstage coupling (formed by a 3686 MHz quartz and resistor R8) between pins 2 and 7. The mixer sees at its IF port a parallel circuit consisting out of R7 and the high input impedance of IC1. L3 and C9 form a parallel resonant circuit that is tuned to the IF. The value of C9 is not critical because the output resistance of IC1 causes strong damping.

The second mixer based on the well-known NE612 and is used as a product detector. The mixer output pins of the NE612 drive the differential input of the NE5532 audio amplifier. Any remaining RF energy present at the output pins is shunted to ground by using the two capacitors C14 and C15. These effectively couple only an AF signal output from the product detector stage into the audio amplifier.

The AF stage has a gain of 60 dB at the 750 Hz audio filter center frequency. The audio filter center frequency is determined by the component values used in the passive series resonant circuit formed by Dr1 and C16. The audio output volume adjustment is controlled with an RF attenuator control P1, located close to the antenna input. The NE5532 output resistance is relatively low, so 60 Ohms headphones can be used without an additional series resistor.

The receiver operates well across a wide range of supply voltages ranging from 9 V to 15 V. The AF amplifier is directly powered from the supply rail. The IF amplifier, second mixer and oscillator need approximately + 8 V. A series voltage-dropping resistor R9 normally meets this requirement. In practice, if the resulting voltage is less than 7 V, reduce the value of R9. Alternatively, one could use a + 8 V voltage regulator in place of R9. Without any input signal, the receiver consumes only a mere 25 mA.

Receiver alignment requires a frequency counter and an oscilloscope. First, measure the 1st oscillator frequency and observe its output voltage at pin 1 of the ring diode mixer. The frequency should be 10686 kHz with C1 at the maximum setting and 10731 kHz at its minimum setting. The measured 1st oscillator (LO) voltage applied to the mixer should measure about 0,5 Vss. If the desired frequency values are not correct, vary C3 and / or C4 slightly. Next adjust the trimmer capacitor C10. It serves to slightly adjust the BFO offset frequency and therefore the resulting received signal AF tone or pitch. The best performance will occur when the BFO frequency offset results in an audio tone of about 750 Hz (matching the passive audio filter resonance (C16 and DR1).

swr meter

my friend  Mr. Rezaee  vswr  meter